Clearglass - some new glass for your bass  [documentation]

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dylan159
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Post by dylan159 »

INTRO
Hello everyone. I'm a fan of the sound of the popular Darkglass pedals, and about a year ago I engaged into making the Fairglass, my first re-adaptation of the VMT and B3K circuits. The Fairglass is still a great sounding pedal and I can't really pick favorites between it and these ones, but the noise could be better even if it's acceptable, and I think I can be more accurate too, while preserving the original goal of making the circuit more compact without compromises. The real holdback was the inverter chip, both for the unavoidable noise and because I can't accept using only one section of a 16 pin chip. There are many other things I wanted to do to the circuit too, reason why I had to find a way around the inverter first. I've already shown a prototype of the Clearglass before, which is to say an alternative circuit that tries to substitute the CMOS clipping with something else, and here it is brought to a point I'm finally satisfied with.
SCHEMATIC
Let's start with the schematics for both so you can stack up on questions before I try to answer them one piece at a time:
clearglass2.PNG
clearglass2bk3.png
THE MU AMP AND THE NOTCH
My first challenge was to replace the mu-amp stage and following Hall notch, both to make it simpler and to save on JFETs, which have become either too small or too expensive. The main thing to notice here is that the notch is an heavy load on the amplifier output, and they behave completely differently than each taken in isolation. This gives some interesting results regarding gain, headroom and frequency response, but also made my job trickier because I had to consider them as one unit.
First, I've built this part as in the original and did some measurements with ARTA and Soundcard Scope. Here's frequency response. These are a bit noisy because I've used a very small input to avoid clipping, although I then tried overdriving it and it led to the same exact results (clipped white noise is still white noise). Here's both the VMT and the B3K in all three modes:
darkglassmuampvmt.png
darkglassmuampbk3all.png
These measurements mostly agree with simulations. As you can see the notch is much more narrower and shallower than if driven by an ideal source. Probing in simulation shows that's because the such loaded mu amp output peaks right next to the notch. Just as interesting, the gain potential of the mu amp is completely gone, and the output is at unity at about 1kHz (red line shows bypass).
I've struggled for a long time to reach a similar response without the mu amp, with bridged T, hall notch, increasing the source impedance, the loading, adding frequency dependent gain, but I couldn't get a notch that was as narrow or as shallow as the original, although I got close, without being overly complex. Then I took a step back and thought “is a notch this narrow even audible or desirable?”. If you account for the encompassing high-pass, the Q of the notch ends up being about 4.5 or more. That's a very narrow notch, a third of an octave bandwidth, way narrower than what's normally used in audio, which can cause inconsistencies in the response (think of some notes sounding differently than the ones next to them!). But is it audible? I've made a similar filter in DAW and tried both clean and before distortion and if it was doing anything, the effect was drowned out when I switched on the highpass too.
So, I've decided to focus on the highpass response! From the measurements for the VMT, the -3dB point seems to be at about 1.3kHz and the slope is a mere 3dB/octave. Making such a gentle filter is actually more challenging than it seems, but I managed to make a good piecewise response with C6...R11.
highpassvmt.png
The B3K was a bit more challenging, because of the switch. Its response, ignoring an even narrower notch, can be summarized by a 8dB/oct lowpass with a cutoff around 250Hz and a treble response that goes between two different lowpass cutoffs and an high shelf. At this point translating this into a circuit that gets close became easy enough. The error is mostly collected below 100hz because of the less steep slope.
highpassb3k.png
That's it for the frequency response, but we're all but done here. As seen from the measurements, the gain is actually not much at all, being unity at 1k (since I've made the response to be the same otherwise, one point is all we need to consider). Since this network has to be before the gain stages, this led me to a couple of interesting choices, the first being of having the filter after just a buffer, which is the same buffer that splits off the clean signal (previously the buffer was in parallel to an op amp amplifier driving this filter for noise reasons). This put me at just -6dB at 1k, and that's why to compensate for this, the gain of the op-amp stage following it has been doubled in gain, while keeping the same frequency response at all gain settings.
The second curious choice is of course D1. The last thing I checked with the mu amp was headroom: it started to show clipping with positive input peaks over 200-300mV, while negative peaks remained clean. No big deal right? Well, for one thing that means I can't get any gain into it because that's already the forward voltage of a schottky and it doesn't go lower than that. The second thing is that the input headroom remained about the same at different frequencies, even if the output amplitude was different because of the filtering. This meant that the diode had to go before the filter, or clipping would be much lower at lower frequencies.
I've checked THD in ARTA on the clean output to be sure the diode load doesn't add undue distortion to that, and the results were indistinguishable from the unloaded output. It sure sounds clean :D. The 1k resistor has been chosen because it doesn't cause frequency response errors in the filter whether the diode is conducting or not.
THE FIRST GAIN STAGE
Not much to say here. Since the input signal is half the original amplitude, I just needed to double the gain and adjust the feedback cap accordingly. The bass cutoff changes with gain the same way in the VMT. Consolidating this with the successive op amp stage is tempting, but I decided to keep them separate because it's hard to get the same frequency response when one stage has a variable cutoff and another doesn't, because when the first op amp eventually clips it'll keep this second clipping source and because it just makes easier for me to analyze the following one separately. NE5532 has been used here because it seems a good choice to keep the noise low, since current noise and bias current aren't a concern at this point of the circuit, but you can use something else.
THE CMOS SURROGATE
Here's the second big hurdle I had to face, and the most important. Since the CMOS inverter was used exactly because of its clipping characteristics, I had to substitute it with something very similar if that's what I was going to do. I've tried about everything, from very nonlinear single ended amplifiers with or without added diodes to discrete MOS inverters. In the end, the trusty op-amp turned out to be the best and more versatile platform once again.
But first I had to set myself a goal, so I breadboarded the CD4049 amplifier with the same values as the original, calibrated the software Soundcard Scope with my multimeter, and used the XY mode to get some sort of transfer curve. This was done with inputs up to 2V peak, with larger capacitors to flatten the frequency response even though the test signal was well in the pass band anyway and this didn't make much of a difference.
2v.jpg
This confirmed the well known fact that the 4049 has an asymmetrical output swing, with the NMOS pulling down harder and off-center bias. This is a very interesting curve, with asymmetrical hard clipping on the negative half and soft clipping on the positive. I've repeated this with both high and low impedance load and it didn't change, confirming that the inverter has good output impedance. I've also repeated the test with different sections.
In addition to this, I've scoped the output and reference waveforms with different inputs from 10 to 400 mV to get the small signal gain (16) and at the same time checked THD to confirm the onset of clipping, which agrees with the picture in being about 200mV peak either way. Also, I've checked the frequency response of the stage in ARTA for both versions:
darkglassCMOS.png
darkglasscmosbk3all.png
You might ask why the cutoffs don't correspond with those calculated from basic op-amp theory. You might also ask why this stage has the same gain in both versions. The reason for both has to do with open-loop gain. We're very far from the ideal infinite gain, in fact it's between 30, the most quoted figure, and 25 which is about what I've calculated from the measured closed loop gain of -16 and the values used. For the first question this means that the input impedance isn't zero, so the cutoffs will be affected. For the second it means that we're operating very close to the open loop gain, with diminishing returns the more we try to increase it. This meant the b3k version, which you might expect to have a gain of -23, instead had about -18. I did measure both and you can see the slope is slightly different for small signals, but they're so close that for the purposes of my approximation they're basically the same, and that's why the resulting stage is the same in both except for frequency response.
To craft this stage I had to give myself some rules in what I was allowed to do with the graphical plots, otherwise I might end up trying everything to line up two very different curves and fool myself into thinking I had reached my goal. They go like this:
-the measured curve evidently has some DC offset due to the asymmetrical waveform. To account for this, I've measured the DC bias to be about 3V. The NMOS can pull down very close to this, but surely not below the negative rail as the -3.5V lower limit can make you think! This means the zero y coordinate is y:-0.5V. The zero x coordinate will be whatever the intersection with the curve is, in this case a bit more than x:-0,5V
-I'm interested in input headroom, since the same input signal has to result in the same clipping, not in the output amplitude, which will just mean the output is just louder or quieter. This means I'm not allowed to scale the x axis (input signal has to be the same), but I'm allowed to scale the y axis, because I'm not interested in the absolute output amplitude, just that the transfer curve changes it proportionally once it starts clipping. I'm also allowed to invert the output, as long a certain input results in a certain amount of clipping and a positive input clips hard while a negative one clips soft.
-this means I can start by setting a threshold for hard clipping, which will be lower than the actual zero by its amount, scale the output by the ratio of this threshold to the original's 3V and the soft clipping region will be scaled by the same amount. The actual value for the threshold isn't important, as long as hard clipping happens with positive input peaks above 200mV (the difference between the zero x coordinate and the hard clipping knee), so that if the curves overlap and the positive input swing from zero is the same, the negative one has to be too (this means the zero point doesn't lie in a different place in both curves); also, once scaled to the same output, the slope for small signal gain has to be the same in both, so that the ratio between clean and clipped gain is preserved.
Even knowing this, the job wasn't easy. I've tried many combinations of hard and soft clipping diodes, resistors and diode ladders, every time scaling them and checking against the original curve, before settling on a rather simple configuration that gave the best results.
The 2.2k output resistor and the chain of two 4148 and a schottky set the hard clipping threshold for positive input peaks. In the simulated XY curve for the whole op amp stage and for a simple configuration of resistor and diodes this ended up being 1.6V which is about what you'd expect from the sum of the forward voltages. This allowed me to account for eventual DC offsets.
The soft clipping wasn't as easy. Feedback diode clipping worked well to approximate most of the curve, as long as I chose the appropriate threshold and gain (this whole exercise turned out being to juggle the hard clipping threshold coordinates against the soft clipping ones, while keeping the small signal gain the same once scaled to the original output), done by D4 in the Mk2 schematic, but wasn't enough by itself, since after clipping gain continued being unity (or actually 1*the scaling factor) forever. In simulation, the op amp eventually running out of output swing provided a good second hard limit, but this wasn't enough in practice, so that's what D8 and D9 are doing a great job at. This leaves out D3, whose job is just to prevent the op amp output to clip on positive peaks. It seems a small thing, since the diode chain is already clipping that, but removing it changed the measured curve drastically, altering both thresholds and making the clipping harder.
isthisit.png
Here's the result, with inverter in yellow and surrogate in red, scaled by about 2 times following the rules I've listed, and inverted since my amplifier is non-inverting (polarity of the clipping threshold is respected, since they're referred to the input: positive peaks hard clip, negative ones soft clip). The slightly quieter input isn't an issue when seen in dB, there's still plenty of output and the volume I ended up setting was still about halfway on the knob.
There's one last thing to get out of the way for the Bk3: since the gain is low, changing the cutoff with the grunt switch in the feedback path leads to premature shelving with a non-inverting amplifier. That's why this has been done at the input instead.
I'm very happy with this result and while this is a specific case, you can apply this method to get inverter-like clipping in other applications too, just by tweaking the gain and the frequency response.
THE FILTERS AND MIXER
Again there are no changes here. The series 2.2k before the diodes has been chosen both for its effect on clipping threshold and softness and because it's a low enough source impedance for the bridged T notch even in the case the diodes aren't conducting. I was tempted to scale down the resistors values in the SK low-pass filters for noise, but doing so in the first one changed the loading on the bridged T altering its response; I could have scaled the second one but I didn't because the difference it makes for noise is irrelevant: the “damage” has already been done when we added all that gain :D. Same thing goes for the volume and blend pot values.
VERO
Here's compact vero layouts for both versions...
clearvmt.png
clearbk3.png
DEMOS
...and demos of both, so I can confirm they sound, and sound good :D

CONCLUSIONS
My goal was to make a Darkglass alternative without using CMOS inverters, also for noise reasons, while accurately reproducing its characteristics. I think I've achieved my goal, while also devising a 4049 replacement stage and trying to combine a new experimental approach to the usual simulations. Let me know if you have any observations or if you try this for yourself.
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Post by Serge75 »

Impressive. You really sucessed getting the vibe out of them, these sound as i remember playing them, still sound as agressive to me as the originals. But thats main ingredient charm for their fans. Congratulations!

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Post by bmxguitarsbmx »

Great work Dylan. Very in depth. Lots of detail in there. I particularly like your analysis of the open vs closed loop gain of the mos inverter stage. I like the sound of the 4049, but haven't play with them in a long time. Did you notice any crossover distortion? Seems like your transfer function did not show any. Possibly some 4049's do and some don't?

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Post by dylan159 »

bmxguitarsbmx wrote: 05 Oct 2021, 17:35 Great work Dylan. Very in depth. Lots of detail in there. I particularly like your analysis of the open vs closed loop gain of the mos inverter stage. I like the sound of the 4049, but haven't play with them in a long time. Did you notice any crossover distortion? Seems like your transfer function did not show any. Possibly some 4049's do and some don't?
Thanks. No crossover, it would have been very noticeable with a 10mV input instead I got a pretty clean sine both in scope trace and THD. A friend thinks inverters biased this way operate in class A/AB which is something that agrees with what is referred in "art of electronics" as shoot-through: both mosfets conduct at the zero crossing.
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Post by x-tn »

dylan159 wrote: 01 Oct 2021, 11:46
THE FIRST GAIN STAGE
On Mk2 schematic, I guess the C7 should be connected to Vr instead of GND.

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Post by dylan159 »

x-tn wrote: 08 Nov 2021, 13:25
dylan159 wrote: 01 Oct 2021, 11:46
THE FIRST GAIN STAGE
On Mk2 schematic, I guess the C7 should be connected to Vr instead of GND.
No, there's no need with a capacitor. Both are AC ground as far as it is concerned, and I like to keep my bias reference clean if possible. If the feedback was DC coupled to save on a capacitor (but no bass shelving!), yes you need to go to your ground or virtual ground.
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Post by x-tn »

OK, thanks. On the traced VMT schematics it's connected to Vr, that's why I thought...

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Post by subbass »

Hi Dylan!

I've been following this since your Fairglass but just about to build one with the intention of making it an onboard fx on my bass.
So, I've got to care about power consumption and had to get this even simpler.

Since I'm going to be using the ClearGlass after active EMGs, I'm omitting the input and output buffers and the blend pot. I'll be running this with the bridge pickup and use the usual blend pot to mix with the neck pickup. A simple low pass filter after the neck before the blend will probably be the best.

Anyway, the real reason of my post is the addition of a second notch filter, getting it a step closer to the original B3K. The schematic below represents some personal choices like omitting the Attack and Grunt switches and using set values.

2nd filter cuts some gain but since this is after clipping and there's still plenty of volume available, it should be fine, right? The plot image doesn't account for diode clipping and volume pot set at 50%. Thank you Dylan!
clearglass-b3k-2notch.jpg
-

I'll be using TL062. With almost 0-noise EMGs and shielded and properly grounded bass cavity, I got no side efects to this low power old chip; at least within the frequencies I like to play around. I got no business high up at 8-10k as the bass, even going full saturation bonkers.

I used them on my heavily modified HAZ preamp, thanks to @George Giblet, + 2 frequency EQ, based on DSM noisemaker's awesome EQalite and @mictester 's amazing Really Cheap Compressor with simple mods.
And all of that already IN the bass with total consumption of about 2-2.5mA running on 2 rechargeable 9Vs. -With charge plug on the bass. haha!
Now ClearGlass has to go in there too. Love you guys! It's a better world with people like you. :applause: :worship:

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Post by dylan159 »

subbass wrote: 25 Nov 2021, 16:10 Hi Dylan!
Cool idea subbass and thanks for your words. I think the TL062 is the right choice for low power consumption, the main differences of concern being G*Bw and noise, while everything else should be still adequate. You're right that the former becomes relevant with all that gain in a single stage, but I don't think the effect should be unpleasant (there will be stuff up there due to clipping, but it gets heavily filtered anyway later).
About the removal of the buffers, for the output you can simply go opamp>capacitor>10k volume pot without the extra output resistors. That should be welcome since space is at a premium. not sure if passive blend of the other pickup is the best way, unless you have something else to take care of that.
About your additional T notch, I'm not sure it gets it closer to the original, but if you like it anyway that's fine: the post-clipping part is identical, so I don't think it's possible to make it any closer, since you can't confound pre-clipping filtering with post-clipping. Anyway I simulated both side by side to see how different they are:
subbass.png
So you're right about making it quieter, you're losing about 20dB in the "sensitive" range! Another important difference is that the bridged T isn't low output impedance, so the low-pass after it gets affected. This can be seen in the treble rolloff being much slower, almost like having just one low pass filter instead of two.
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Post by subbass »

Thanks for the tips again. I'm sure I'll be changing values once that's in my hand and working and give it some more juice through "attack and grunt" values perhaps. Actually the output will be going through a preamp which is practically a 4 band, and then the compressor which shapes things even more, slightly on the low and high ends.

I tried to match this to JohnK's analyses, attached below. That's some hefty double-scoop but responsible of that specific tone when mixed with clean deep bass after, IMO.
B3Kfreqtest.jpg
I also tried the 10x caps, /10 resistors method on the notch filters but cap values become too sensitive. Slightest change can screw things up. May be not an issue for someone measuring every cap before soldering(me, lol) but probably not generally acceptable as tolerances go. :D

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Post by dylan159 »

I think this AC analysis is doing exactly what I was talking about: confounding pre and post clipping filtering in one lot. You can refer to my original post about the very narrow pre clipping notch caused by the loading on the mu amp and my decision to skip it altogether (this was supported by testing in daw so it's not just theory). I think trying to replicate it post clipping can only bring it further away from the original, if that's the goal, also because a bridged T can't achieve a notch that is both so narrow and so shallow.
About the impedance scaling, even if capacitors usually have worse tolerances than resistors, this shouldn't be a case for worry. Tolerances are in proportion to nominal value, so (someone tell me if I'm wrong), they would appear as coefficients in the design equations, in particular for cutoffs we usually see a RC product, so it doesn't matter if it's the resistor or the capacitor which has the worse tolerance. In any case, pedals aren't a case for accuracy, as shown by my systematic use of mostly E6 values, because with some care that usually allows me to get within one dB of my goal, which is more than enough. It would be different if I were designing something like a RIAA eq.
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Post by subbass »

Tolerances are in proportion to nominal value
Oh man, I've got some 2.2n caps that measure as high as 6.8-7n and a bag of 47n caps, of which, non is lower than 60n. Frickin bad batches or some mislabeled stuff. Such bad parts cause some paranoia.

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Post by jhergonz »

Darkglass tone without CMOS? Nice! I like it, thanks for sharing this circuit.

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Post by dylan159 »

Little update, but I figured someone might be interested in how I finally realized this: very DIY and very wood enclosure and knobs made from plywood scraps and a dowel, with shielded internals.
_IGP4476.jpg
20220115_211202.jpg
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Post by HENK »

Thanks for this.
Have You played it with a Guitar?

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Post by dylan159 »

HENK wrote: 18 Mar 2022, 07:42 Thanks for this.
Have You played it with a Guitar?
Not yet. I did with the fairglass and it wasn't that great, you start to notice how scooped it really is. This is different enough that it might work though.
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